• 专利附录
  • 专利说明
  • 权利要求
  • 类似技术
  • 同族专利
  • 引用文献
  • 法律状态
  • 优先权
    • 专利摘要:
    A circuit arrangement for operating a luminous means (3) comprises an input and a power factor correction converter. The converter has an inductor (21), a controllable switching means (23) connected in series with the inductor (21), and a regulator (13, 30). The controller (13, 30) comprises a PI element. The controller (13, 30) is arranged to produce a phase shift for a signal component of an input signal of the regulator (13, 30) whose frequency is twice as high as a frequency of an input voltage.
    公开号:AT15822U1
    申请号:TGM9017/2014U
    申请日:2014-04-25
    公开日:2018-07-15
    发明作者:Schönberger John
    申请人:Tridonic Gmbh & Co Kg；
    IPC主号:
    专利说明:

    description
    CIRCUIT ARRANGEMENT AND METHOD FOR OPERATING A LUMINAIRE The invention relates to a circuit arrangement and a method for operating a lamp. The invention particularly relates to circuit arrangements that include a converter that is operated to provide power factor correction.
    With the increasing spread of lamps such as LEDs and LED modules, circuit arrangements for operating such lamps continue to gain in importance. A power factor correction is used in operating devices for such lamps in order to reduce the undesired generation of harmonic currents in the supply network. The power factor is a measure of harmonic currents generated by the operating circuit.
    Depending on the particular application of the operating circuit, different solutions for power factor correction (PFC, "Power Factor Conversion") can be selected. For example, a power factor correction circuit can be provided as an input stage between a rectifier and a transformer. The power factor correction circuit can operate, for example, on the principle of a step-up converter.
    So-called single-stage PFC converters can also be used, which perform the power factor correction in addition to a transformation. An example of a one-stage PFC converter is a one-stage PFC flyback converter. Circuit arrangements of this type can be used in particular in applications which do not require particularly large powers.
    In operating circuits with voltage regulation, voltage ripples on the output side, which oscillate at twice the mains frequency, can have a negative influence on the power factor correction. For example, an attempt to regulate voltage ripple on the output side can, in conventional control loops, result in harmonic currents not being reduced to the desired extent. One approach to solving these problems can be to suppress the voltage ripple on the output side. For this purpose, an output capacitor with a large capacitance can be provided on the output side. Alternatively or additionally, a controller with a small bandwidth can be used. However, such approaches can have various disadvantages. For example, the use of a large capacity capacitor as an output capacitor may be undesirable because of the size of the component and / or because of possible cost disadvantages.
    The invention has for its object to provide devices and methods in which a good power factor correction can be achieved without that voltage ripple on the output side of a converter must be suppressed by an output capacitor with a large capacitance. The invention has for its object to provide such devices and methods that can be used in PFC converters with voltage control.
    A circuit arrangement for operating a lamp and a method having the features specified in the independent claims are provided. The dependent claims define embodiments of the invention.
    According to embodiments of the invention, a controller is used in a circuit arrangement for operating a lamp, which comprises a PI (proportional-integral) member and which is configured to a signal component of an input signal of the controller, which oscillates at twice a supply voltage frequency to impress an additional phase shift. It has been shown that a good power factor correction can be achieved by the phase shift of the signal component, which oscillates at twice a supply voltage frequency, even if this voltage ripple on the output side is not strongly suppressed.
    A particularly good power correction can be achieved if the phase shift 1/16
    AT15 822 U1 2018-07-15 Austrian patent office
    Shift at the frequency that is twice the supply voltage frequency, in an interval of -90 ° and / or approximately -90 °. This allows the use of a smaller output capacitor and / or a controller with a wider bandwidth than in conventional control strategies that do not specifically introduce an additional phase shift.
    To generate the corresponding phase shift, the controller can be designed so that a transfer function of the controller has two poles at frequencies that are in an environment of the frequency that is equal to twice the supply voltage frequency.
    A circuit arrangement for operating a lamp according to an embodiment includes an input for receiving an AC voltage with a first frequency. The circuit arrangement comprises a converter with power factor correction, which has an inductor, a controllable switching means which is connected in series with the inductor, and a regulator. The controller has a PI element and is set up to generate a phase shift for a signal component which has a second frequency which is twice as large as the first frequency.
    The PI element has the behavior of a conventional PI controller, but is supplemented in the controller by components for introducing an additional phase shift. The controller can include the PI element, a first pole and a second pole.
    The first pole and the second pole may be at a frequency or at frequencies in an environment of the second frequency, i.e. close to twice the supply voltage frequency. The first pole and the second pole can be double poles or a second order pole.
    The frequencies at which the poles are located can be less than a frequency with which the controllable switching means is switched in a clocked manner.
    The controller can include electrical isolation.
    [0017] The converter can have an input side with the inductance and an electrically isolated output side. The PI element can be provided on the output side of the converter. A filter, the transfer function of which has the first pole and / or the second pole, can be provided on the input side of the converter.
    The controller can be set up so that the phase shift for the signal component, which oscillates at twice the frequency of the supply voltage, lies in an interval of a phase shift of -90 °. The controller can be set up in such a way that the phase shift for the signal component oscillates at twice the frequency of the supply voltage by less than a predetermined threshold value of -90 °.
    The controller can be set up so that the phase shift for the signal component is -90 °.
    [0020] The circuit arrangement can comprise an integrated circuit for controlling the controllable switching means. The integrated circuit may have an input to receive a signal that contains the signal component that is phase-shifted by the controller.
    The integrated circuit can be set up to control the controllable switching means so that an on-time and / or an off-time of the controllable switching means depend on the respective phase of the phase-shifted signal component.
    The integrated circuit can be set up to control the controllable switching means in such a way that a voltage at an output of the circuit arrangement is regulated to a desired value. The controlled variable can be a variable recorded on the output side of the controller, for example the output voltage itself. The controlled variable can also be a variable on the input side, i.e. a primary variable of the converter. The auxiliary size can
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    Patent office can be regulated to set the output voltage to a desired value. The
    Auxiliary variable can, for example, be recorded with an auxiliary turn on the input side.
    The converter can be a flyback converter which is connected to the input via a rectifier.
    [0024] The converter can be a PFC flyback converter.
    The circuit arrangement can be an operating circuit for at least one light-emitting diode. The circuit arrangement can form an LED converter or can be comprised by an LED converter.
    According to a further exemplary embodiment, a system is specified which comprises the circuit arrangement according to one exemplary embodiment and at least one light-emitting diode which is connected to an output of the converter. The at least one light emitting diode can comprise at least one inorganic light emitting diode and / or at least one organic light emitting diode. The at least one light-emitting diode can be connected to the output of the converter via a converter circuit which is connected between the output of the converter and the at least one light-emitting diode.
    According to a further embodiment, a method for operating a lamp with a circuit arrangement is specified, which is supplied with an alternating voltage at a first frequency and which comprises a converter. To operate the illuminant, a controllable switching means, which is connected in series with an inductance of the converter, is switched in a clocked manner. The method includes voltage regulation with a regulator that has a PI element. In voltage regulation, the controller creates a phase shift for a signal component that has a second frequency that is twice the first frequency.
    Further features of the method according to exemplary embodiments and the effects achieved thereby correspond to the further features of the circuit arrangement according to exemplary embodiments.
    The method can be carried out with the circuit arrangement according to an embodiment.
    The circuit arrangement and the method according to exemplary embodiments use a control strategy in which the controller specifically causes a specific phase shift at least for those signals and signal components whose frequency is twice the supply voltage frequency. In addition to the PI element, the controller can comprise at least one filter which causes the corresponding phase shift for signals and signal components which oscillate at twice the supply voltage frequency. The at least one filter can have two poles. The poles can be approximately twice the supply voltage frequency.
    Such a controller can also be referred to as "PI + PP" or "PIPP" controller, since it has two poles in addition to the PI element.
    This control strategy allows a good power factor correction without the voltage ripples, which oscillate at twice the supply voltage frequency, being suppressed on the output side by an output capacitor with a large capacitance and / or having to be removed in the voltage control by a regulator with a small bandwidth. The control strategy can be used in particular for PFC flyback converters.
    The invention is explained below with reference to the figures based on preferred embodiments. In the figures, identical reference symbols designate identical elements.
    Figure 1 [0035] Figure 2 shows a system according to an embodiment.
    shows a circuit diagram of a circuit arrangement according to an embodiment.
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    AT15 822 U1 2018-07-15 Austrian Patent Office [0036] Figure 3 [0037] Figure 4 [0038] Figure 5 [0039] Figure 6 [0040] Figure 7 [0041] Figure 8 [0042] Figure 9 [0043] Figure 10 Figure 11 is a block diagram representation of a controller according to one embodiment.
    10 is a block diagram representation of a controller according to an embodiment.
    shows voltage ripple of a signal generated by the controller according to an embodiment.
    shows a signal generated by the controller according to an embodiment together with an input signal of the controller.
    shows a Bode diagram for a controller of a circuit arrangement according to an embodiment and for a conventional controller.
    shows an input current of a circuit arrangement according to an embodiment.
    shows an input current of a conventional circuit arrangement in which an output capacitor with a larger capacitance than in Figure 8 is used.
    shows a circuit diagram of an implementation of a controller according to an embodiment.
    shows a circuit diagram of a circuit arrangement according to a further embodiment.
    Figure 1 shows a representation of a system 1, which includes an operating device with a circuit arrangement 2 for operating a lamp 3. The illuminant 3 can comprise at least one light-emitting diode (LED). The illuminant 3 can comprise several LEDs. The LEDs can be inorganic or organic LEDs.
    The circuit arrangement 2 has an input 10 to which a supply voltage is supplied. The supply voltage is an AC voltage, for example a mains voltage. A frequency of the supply voltage at input 10 is also referred to here as the supply voltage frequency or as the first frequency. Twice the supply voltage frequency is called the second frequency. This second frequency plays a role in the control strategy of the circuit arrangement 2.
    The circuit arrangement 2 comprises a rectifier 11, which provides a rectified AC voltage to a converter 12. The converter 12 can be configured as a power factor correction (PFC) converter, which is operated in such a way that it reduces the return of harmonic currents into the network. The converter 12 can be a flyback converter, for example. Other types of transducers can be used. An output of the converter can be connected to the illuminant 3. The illuminant 3 can be connected to an output connection 14 of the circuit arrangement 2. The illuminant 3 can be connected directly to an output connection 14 of the circuit arrangement 2. Alternatively, a converter circuit can be connected between the output connection 14 and the lamp 3, which preferably controls the current or the power of the lamp 3. This converter circuit can be formed, for example, by a buck converter (buck converter), a boost converter (boost converter) or an inverter circuit (buck boost converter).
    The converter 12 has a controller 13. The regulator 13 can be a voltage regulator. The controlled variable of the controller 13 can be, for example, the output voltage of the converter 12 or an auxiliary variable that is related to the output voltage of the converter 12.
    As will be described in detail with reference to FIGS. 3 to 11, the controller 13 has a PI (proportional-integral) element. The controller is set up so that it causes a certain phase shift for an input signal whose frequency is twice the supply voltage frequency. Generated from the input signal from the controller4 / 16
    AT15 822 U1 2018-07-15 Austrian patent office te output signal can, for example, a phase shift of -90 ° compared to
    Have input signal that oscillates at the second frequency, ie twice the supply voltage frequency.
    The phase shift caused by the controller 13 for a sinusoidal signal as a function of the frequency of the signal can be defined by the phase response of a transfer function of the controller 13. The transfer function can be defined as the quotient of the output variable of the controller 13 transformed into the frequency range and the input variable of the controller 13 transformed into the frequency range. The complex argument of the transfer function, i.e. the phase shift, as a function of frequency defines the phase response. The controller 13 can be configured such that the phase response of the controller 13 has a value of -90 ° or is approximately equal to -90 ° at the second frequency, which is twice the supply voltage frequency.
    Figure 2 shows a circuit diagram of a circuit arrangement 2 according to an embodiment in which the converter is designed as a flyback converter. Such converters are also referred to as flyback converters or step-down converters.
    The converter has a transformer, which may include a primary-side inductor 22 and a secondary-side inductor 25. A primary side of the converter has a main inductance 21 in which energy can be stored. The primary-side inductor 22 and the main inductor 21 are shown schematically separately in FIG. 2, but need not be separate components. For example, only a single coil can be provided, which performs the function of the main inductor 21 and the primary inductor 22 of the transformer. The primary inductor 22 of the transformer can be a leakage inductor.
    The converter has a controllable switching means 23 which is connected in series with the main inductor 21. The controllable switching means 23 is switched during operation of the converter in order to transfer energy from the primary side of the transformer, which is the input side of the converter, to the secondary side, which is the output side. When the controllable switching means 23 is switched on, energy is stored in the main inductor 21. This state is also referred to as the leading phase or charging phase, in which the main inductor 21 is charged with energy. When the controllable switching means 23 is switched off, the temporarily stored energy is transmitted to the secondary side. This phase is also called the blocking phase.
    The secondary side has a rectifier, which can comprise a diode 26 or more diodes. An output capacitor 27 on the secondary side can be charged when energy is transferred from the primary side to the secondary side. The capacitor 27 is also referred to as a charging capacitor.
    The controllable switching means 23 can be a transistor. The controllable switching means 23 can be a power transistor. The controllable switching means 23 can be, for example, a bipolar transistor, a transistor with an insulated gate electrode, a field effect transistor or another controllable switch.
    The circuit arrangement 2 has a voltage control loop 30. The voltage control loop 30 can use a voltage Vo on the output side as a controlled variable. The voltage Vo on the output side can be tapped at a point 28, for example via an ohmic voltage divider. A reference source 31 can specify a target value Vo_ref. A differential amplifier 32 or subtractor can determine the deviation between the voltage Vo on the output side and the target value. The controller 13 can switch the controllable switching means 23. Depending on the deviation that is supplied to the controller 13, for example an on time of the controllable switching means and / or an off time of the controllable switching means can be changed in order to regulate the voltage Vo on the output side in the direction of the setpoint. For example, the ratio of on-time (t on ) to off-time (t of f) can be set depending on which control signal the controller 13 generates from it
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    Patent Office supplied input signal generated.
    The output side voltage Vo may have voltage ripple at the second frequency that is twice the supply voltage frequency. Such voltage ripple are caused by the rectification, which provides a rectified AC voltage to the converter 12.
    While conventional control strategies try to keep the amplitude of this voltage ripple on the output side small and / or to dampen a transmission of this voltage ripple by the controller 13, in embodiments of the invention this voltage ripple is provided with a phase shift and is used specifically to correct the power factor to improve.
    Figure 3 is a block diagram of components of a controller according to an embodiment. The controller has a PI element 41.
    [0060] The controller has at least one component 42 for causing an additional phase shift. The at least one component 42 may include one or more filters.
    The at least one component 42 causes a signal which oscillates at twice the supply voltage frequency to be provided with an additional phase shift. An output signal Vc of the combination of the PI element 41 and the at least one component 42 for causing the additional phase shift has a specific phase shift with respect to the corresponding input signal. This phase shift is used for the second frequency, i.e. the frequency of the voltage ripple, selected such that the phase-shifted voltage ripple in the output signal Vc reduces the total harmonic distortion (THD, “total harmonic distortion”) of the input current and / or the input voltage.
    The at least one component 42 for causing the additional phase shift can have a transfer function that has two poles. The two poles can be in an environment of the second frequency that is twice the supply voltage frequency.
    The output signal Vc of the combination of the PI element 41 and the at least one component 42 for causing the phase shift can influence a switch controller 43. The switch control 43 can switch the controllable switching means 13 clocked. Switching the controllable formwork on and off can vary depending on the time with the phase-shifted voltage ribs on the output side. These phase-shifted voltage ripples are contained in the output signal Vc, which provides the combination of the circuit element 41 and the at least one component 42 for causing the additional phase shift.
    [0064] Switch controller 43 may be an integrated circuit. The switch controller 43 can be configured as a processor, a microprocessor, a controller, a microcontroller or an application-specific special circuit (ASIC, “Application Specific Integrated Circuit”).
    Figure 4 shows an implementation of the controller for a control device according to an embodiment. The controller has the PI element and components 45, 46. Components 45, 46 can each be an analog filter or a digital filter. The components 45, 46 each define a pole of the transfer function. For example, filter 45 may have a transfer function that has a first pole. The filter 46 may have a transfer function that has a second pole. The first pole and the second pole may be in an environment of the second frequency that is twice the supply voltage frequency. The first pole and the second pole can be twice the supply voltage frequency.
    A large number of further configurations of the controller can be used in exemplary embodiments
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    AT15 822 U1 2018-07-15 Austrian patent office can be used. For example, two poles of the transfer function can also be provided by only one filter that has double poles. While functional blocks are shown in FIGS. 3 and 4, the different components do not have to be separate
    Elements. For example, a digital processor can take on both the function of the PI controller and the generation of the additional phase shift.
    The use of the filters or other components that provide the first pole and the second pole causes a phase shift of approximately -90 ° for signals whose frequency is twice the supply voltage frequency. For the closed control loop there is a total shift of -180 °.
    The PI element and the component of the controller which causes the additional phase shift can be implemented by analog circuit elements or in digital technology. The order of the different components can be reversed. For example, the additional phase shift can be introduced before a signal is fed to the PI element. A filter or both filters, which provide the two poles of the transfer function, can be arranged in front of the PI element.
    The controller can also include electrical isolation. This allows some of the components of the controller to be located on the secondary side and others of the components of the controller to be located on the primary side.
    Figure 5 shows a signal 51 at the output of components 41, 42 of Figure 3 or at the output of components 41, 45, 46 in Figure 4 when an input signal of the regulator has voltage ripples which oscillate at twice the supply voltage frequency. This signal 51 can be used as a control signal on which the switching of the controllable switching means 23 depends.
    Shown with a broken line is a signal 52 at the output of a PI element in a conventional controller if no additional phase shift is introduced. The signal 51 has a phase shift 53, which is caused by the two poles in the transfer function of the controller at twice the supply voltage frequency.
    The phase shift 53 shows the change in the phase position of a controller, which is used in exemplary embodiments, compared to a conventional PI controller without additional phase shift.
    Figure 6 shows the signal 51 at the output of components 41, 42 of Figure 3 or at the output of components 41, 45, 46 in Figure 4 together with the corresponding input signal 55 of the controller. The input signal 55 has voltage ripples that correspond to the voltage ripples on the output side of the converter.
    The signal 51 has a phase shift 59 of approximately -90 ° with respect to the input signal 55. The phase shift 59 is caused by the two poles in the transfer function of the regulator at twice the supply voltage frequency.
    Figure 7 shows a Bode diagram for the controller according to an embodiment in which an additional phase shift is introduced. The Bode diagram for the controller according to one embodiment is shown in solid lines. The Bode diagram for a conventional PI controller is shown for comparison with dashed lines.
    A phase response 61 of a controller according to one embodiment is shown in the lower part of the Bode diagram. The second frequency 60 is twice the supply voltage frequency. The absolute value of this second frequency depends on the supply voltage frequency, can be different for different supply sources and is not important for the explanations below. The phase response 61 corresponds to the complex argument of the transfer function of the controller according to one embodiment,
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    AT15 822 U1 2018-07-15 Austrian patent office where an additional phase shift is generated.
    At the second frequency 60, the phase response 61 has a function value that lies in an interval 63. The interval 63 defines an environment of a phase shift of -90 °. An absolute amount of the difference between the interval limits of the interval 63 can be less than 90 °. The interval 63 can extend symmetrically around the value of -90 °.
    In a closed control loop, this behavior leads to a total phase shift of -180 ° at the second frequency 60. Voltage ripples on the output side are converted into a control voltage by the PI controller with the additional phase shift. The voltage ripple in the control voltage that affects switching of the controllable switching means of the converter can reduce the overall harmonic delay. This applies at least as long as the amplitude of the voltage ripple does not become too large.
    The function value of the phase response 61 at the second frequency 60 indicates the phase shift which a sinusoidal signal experiences through the combination of the PI element with the additional phase shift.
    The phase response 61 of the controller, which is used in exemplary embodiments, can be strictly monotonically falling at the second frequency 60. This can be achieved by an appropriate choice of the additional poles of the transfer function that lead to the phase shift.
    The phase response 61 of the controller, which is used in exemplary embodiments, can have a local maximum at a frequency that is lower than the second frequency 60. It can thereby be achieved that the phase shift at the second frequency 60 lies in the interval 63 by the value -90 °.
    A phase response 62 of a conventional PI controller without additional phase shift is also shown in the lower part of the Bode diagram for comparison. The phase response 62 differs significantly from the phase response 61. At the second frequency 60, the phase response 62 has a larger (and smaller amount) value than the phase response 61.
    The upper part of the Bode diagram shows the gain 64 of the controller used in exemplary embodiments and the gain 65 of a conventional PI controller without additional phase shift.
    As has been described, the additional phase shift with which the voltage ripples are provided by the controller means that the voltage ripples can even reduce the overall harmonic delay. It is not necessary to reduce voltage ripple in the control signal that the regulator generates by using a large capacitance output capacitor and / or using a small bandwidth regulator.
    FIG. 8 shows an exemplary time profile of an input current 71 for a switching arrangement according to an exemplary embodiment. FIG. 9 shows an exemplary time profile of an input current 72 for a switching arrangement with a conventional PI controller, in which no additional phase shift is generated. The input current 72 from FIG. 9 (conventional PI controller) was determined for a converter with an output capacitor whose capacitance was more than twice as large as the capacitance of the output capacitor in the circuit arrangement according to one exemplary embodiment, for which the input current 71 shown in FIG. 8 was determined.
    Despite the significantly smaller capacitance of the output capacitor, the overall harmonic delay for the circuit according to one exemplary embodiment (input current 71 from FIG. 8) is smaller than in the conventional converter (input current 72 from FIG. 9).
    Figure 10 is a circuit diagram illustrating an implementation of a controller in exemplary embodiments.
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    AT15 822 U1 2018-07-15 Austrian
    Patent Office The controller has a PI element 80, a filter 81 for defining a first pole of the transfer function and a further filter 82 for defining a second pole of the transfer function. The poles in the transfer function, which are introduced by the filters 81, 82, are in an environment of twice the supply voltage frequency. The PI element can, for example, have a capacitance 83 in a series connection with a resistor 84. The filter 81 can have a capacitance 85. The further filter 82 can have a further capacitance 86 and a further resistor 87.
    The controller has electrical isolation. For example, an optocoupler 90 can be provided between the primary side and the secondary side of the converter. Other galvanic isolation elements can be used. In the implementation shown, the PI element 80 and the filter 81 are on the secondary side. The further filter 82 is arranged on the primary side.
    [0090] The optocoupler 90 can be connected to a voltage source 91 via a resistor 92. An output of the combination of PI element 80 and filter 81 is connected to an input side of optocoupler 90. An operational amplifier 93 can define a voltage reference. The operational amplifier 93 can keep a current at the output of the optocoupler 90 constant.
    A voltage present at a photodiode of the optocoupler 90 is provided by a voltage source 94 via a voltage divider with resistors 95, 96. A current flowing through the photodiode is supplied to an input of an operational amplifier 99 via a resistor 97. A voltage source 98 can provide a reference voltage to another input. The further filter 82 can be connected to the input and the output of the operational amplifier 99.
    The signal Vc provided at the output of the operational amplifier can be used to control switching operations of the controllable switching means of a converter. For example, the ratio between on-time and off-time can be changed depending on the signal Vc. Voltage ripples in the signal Vo, which represents the voltage on the output side, are present with a corresponding phase shift in the signal Vo and influence the switching of the controllable switching means.
    Numerous further implementations of the various components of the controller can be used in further exemplary embodiments. Other configurations of the PI gate and the filters 81, 82 can be used. The PI element 80 and the filter 81 can be arranged on the primary side. The voltage Vo on the output side can be transmitted to the primary side via an optocoupler or another electrical isolation.
    In other configurations, a different controlled variable can also be used to carry out a voltage regulation. For example, a voltage can be detected on the primary side, which depends on the voltage on the output side. The voltage on the output side can be regulated indirectly by regulating the voltage detected on the primary side.
    FIG. 11 is a circuit diagram of a circuit arrangement according to an exemplary embodiment. An auxiliary inductor 101 can be inductively coupled to the secondary-side inductor 25. A voltage across the auxiliary inductor 101 can be detected. For example, the corresponding voltage can be supplied to the voltage control loop 30 as an auxiliary signal Vaux via an ohmic voltage divider 102. A reference voltage source 31 provides a signal Vaux_ref, which represents the target value.
    In addition to an input 105, at which the auxiliary signal Vaux or the deviation of the auxiliary signal from the desired value is received, the controller 13 can have further inputs. For example, the controller 13 can have an input 107 in order to recognize when the main inductance 21 is demagnetized. Switching operations can be triggered depending on when the main inductor 21 is demagnetized. The controller 13 controls an off 9/16
    AT15 822 U1 2018-07-15 Austrian patent office aisle 106 a control signal with which the controllable switching means 23 is controlled.
    While exemplary embodiments have been described with reference to the figures, modifications can be implemented in further exemplary embodiments. For example, the controller, which specifically introduces an additional phase shift for voltage ripple, can also be implemented in digital technology. A corresponding regulation, in which an additional phase shift for voltage ripple is specifically introduced, can be used for different converter types. Methods and devices according to exemplary embodiments can be used in operating devices for illuminants, for example in an LED converter.
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    权利要求:
    Claims (16)
    [1]
    Expectations
    1. A circuit arrangement for operating a lamp (3), comprising:
    an input (10) for receiving an AC voltage with a first frequency, a converter (12) with power factor correction, the inductor (21), a controllable switching means (23) which is connected in series with the inductor (21), and one Regulator (13, 30; 41-43; 41, 43, 45, 46; 80-83) comprises, the regulator (13, 30; 41-43; 41, 43, 45, 46; 80-83) a Pl Member (41; 80) and configured to generate a phase shift (56) for a signal component of an input signal of the controller (13, 30; 41-43; 41, 43, 45, 46; 80-83), the has a second frequency (60) that is twice the first frequency.
    [2]
    2. Circuit arrangement according to claim 1, wherein the controller (13, 30; 41-43; 41, 43, 45, 46; 80-83) the PI element (41; 80) and a transfer function with a first pole and a second Pole includes.
    [3]
    3. The circuit arrangement according to claim 2, wherein the first pole and the second pole lie in an environment of the second frequency (60).
    [4]
    4. Circuit arrangement according to claim 2 or claim 3, wherein the converter (12) has an input side with the inductor (21) and a galvanically isolated output side thereof, wherein the PI element (41; 80) on the output side of the converter (12) is provided and a filter (82), the transfer function of which has the second pole, is provided on the input side of the converter (12).
    [5]
    5. Circuit arrangement according to one of the preceding claims, wherein the controller (13, 30; 41-43; 41, 43, 45, 46; 80-83) is set up such that the phase shift (56) for the signal component in an interval ( 63) by a phase shift value of -90 °.
    [6]
    6. Circuit arrangement according to one of the preceding claims, wherein the controller (13, 30; 41-43; 41, 43, 45, 46; 80-83) is set up such that the phase shift (56) for the signal component is approximately equal to -90 ° is.
    [7]
    7. Circuit arrangement according to one of the preceding claims, wherein the circuit arrangement comprises an integrated circuit (43) for driving the controllable switching means (23), the integrated circuit having an input to receive the phase-shifted signal component (51).
    [8]
    8. Circuit arrangement according to claim 7, wherein the integrated circuit (43) is set up to control the controllable switching means (23) such that an on-time and / or an off-time of the controllable switching means (23) from a phase of depend phase-shifted signal component (55).
    [9]
    9. Circuit arrangement according to one of the preceding claims, wherein the converter (12) is a flyback converter which is connected to the input (10) via a rectifier (11).
    [10]
    10. Circuit arrangement according to one of the preceding claims, wherein the circuit arrangement (2) is an operating circuit for at least one light-emitting diode (3).
    5 sheets of drawings
    [11]
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    1.5
    FIG. 1
    FIG. 2
    Μ Μ
    [12]
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    2.5
    FIG. 3
    FIG. 4
    FIG. 5
    [13]
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    3.5
    Phase (°) gain (dB)
    FIG. 7
    [14]
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    4.5
    FIG. 9
    FIG. 10
    [15]
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    5.5
    FIG. 11 • Ί IN · N -
    [16]
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    同族专利:
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    WO2014172733A1|2014-10-30|
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    引用文献:
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    US5677602A|1995-05-26|1997-10-14|Paul; Jon D.|High efficiency electronic ballast for high intensity discharge lamps|
    US6577512B2|2001-05-25|2003-06-10|Koninklijke Philips Electronics N.V.|Power supply for LEDs|
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    BRPI1007441A2|2009-01-27|2019-09-24|Led Roadway Lighting Ltd|power supply for LED road lighting fixture.|
    US8492988B2|2009-10-07|2013-07-23|Lutron Electronics Co., Inc.|Configurable load control device for light-emitting diode light sources|
    DE102011109333B4|2011-08-03|2013-04-11|Diehl Aerospace Gmbh|Electric supply device with current shaping signal and method for operating the electrical supply device|
    CN103023300B|2011-09-26|2015-03-18|英飞特电子（杭州）股份有限公司|Constant-current control circuit capable of correcting power factors and power factor correcting circuit|
    CN104054226B|2011-10-17|2018-01-12|金斯顿女王大学|Pulsation neutralizing converter with high power factor|DE202017102691U1|2017-05-05|2018-08-07|Tridonic Gmbh & Co Kg|Buck-boost converter with improved THD behavior|
    法律状态:
    2020-12-15| MM01| Lapse because of not paying annual fees|Effective date: 20200430 |
    优先权:
    申请号 | 申请日 | 专利标题
    DE102013007278|2013-04-26|
    PCT/AT2014/000091|WO2014172733A1|2013-04-26|2014-04-25|Circuit arrangement and method for operating an illuminant|
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